Bidirectional dc-dc converter and control method thereof

ABSTRACT

Disclosed is a small-size, high-efficiency, isolated, bidirectional DC-DC converter. The bidirectional DC-DC converter includes a transformer in which windings are magnetically coupled, switching circuits, a diode which is connected in parallel with a switch, smoothing capacitors, and a control section. First and second DC power supplies, which are connected in parallel with the smoothing capacitors, respectively, provide bidirectional electrical power transfer. When electrical power is to be transferred from the first DC power supply to the second DC power supply, the switch is maintained in the ON state. When, on the other hand, electrical power is to be transferred from the second DC power supply to the first DC power supply, the switch is maintained in the OFF state to prevent a reverse electrical power flow from the first DC power supply.

CROSS-REFERENCE TO RELATED PATENT APPLICATIONS

Japan Priority Application 2008-224231, filed Sep. 2, 2008 including thespecification, drawings, claims and abstract, is incorporated herein byreference in its entirety. This application is a Continuation of U.S.application Ser. No. 13/344,039, filed Jan. 5, 2012, incorporated hereinby reference in its entirety, which is a Continuation of U.S.application Ser. No. 12/544,107, filed Aug. 19, 2009, (now U.S. Pat. No.8,378,646 issued Feb. 19, 2013) incorporated herein by reference in itsentirety.

BACKGROUND OF THE INVENTION

(1) Field of the Invention

The present invention relates to a bidirectional DC-DC converter havingan isolation function. The present invention also relates to a methodfor controlling the bidirectional DC-DC converter.

(2) Description of the Related Art

In recent years, increased use of highly efficient hybrid vehicles ispromoted due to a rising demand for global environment conservation. Thehybrid vehicles have a main battery for driving a traction motor and anauxiliary battery for driving accessories. The degree of freedom indesigning a vehicle power supply system can be increased when the twobatteries, which differ in voltage, are flexibly used for effectiveelectrical power distribution.

In view of the above circumstances, a bidirectional DC-DC converterdisclosed in JP-A No. 2002-165448 provides bidirectional electricalpower conversion between two power supplies that differ in voltage. Thisconverter is configured so that a high-voltage circuit is connected to alow-voltage circuit through a transformer. Operating a switching devicein the high-voltage circuit supplies electrical power from ahigh-voltage power supply to a low-voltage power supply. Operating aswitching device in the low-voltage circuit supplies electrical powerfrom the low-voltage power supply to the high-voltage power supply.

A bidirectional DC-DC converter disclosed in JP-A No. 2006-187147 isconfigured so that a low-voltage circuit is connected to a voltage clampcircuit, which includes a series connection between a switching deviceand a capacitor. This converter uses the voltage clamp circuit to reducea circulating-current-induced loss during a voltage decrease. Further,this converter makes it possible to decrease the dielectric strength ofthe switching device by suppressing the occurrence of a surge voltage inthe low-voltage circuit during a voltage increase/decrease, and servesas a highly efficient, small-size, bidirectional DC-DC converter.

A bidirectional DC-DC converter disclosed in JP-A No. 2004-282828 isconfigured so that an LC resonant circuit is connected in series with atransformer winding. This converter exhibits low switching loss, makesit possible to eliminate the possibility of a large current flowing to aswitching device upon power on/off, and serves as a bidirectional DC-DCconverter that efficiently provides flexible electrical powerdistribution between two DC power supply systems through the use of asimple control scheme.

SUMMARY OF THE INVENTION

In general, downsizing and efficiency improvement of a bidirectionalDC-DC converter can be effectively accomplished by using a switchingdevice that exhibits fast switching characteristics. However, even whena high-voltage MOSFET is used as the switching device in order totransfer electrical power to and from a high-voltage DC power supply andachieve downsizing and efficiency improvement of the aforementionedpreviously disclosed bidirectional DC-DC converters, such downsizing andefficiency improvement are obstructed because the body diode reverserecovery characteristics of the MOSFET are slower than the switchingcharacteristics of the MOSFET.

An object of the present invention is to provide a small-size,high-efficiency, bidirectional DC-DC converter that permits the use of ahigh-voltage MOSFET or other switching device having fast switchingcharacteristics and relatively slow body diode reverse recoverycharacteristics, exhibits low switching loss, and reduces the influenceof relatively slow body diode reverse recovery characteristics. Anotherobject of the present invention is to provide a method for controllingsuch a bidirectional DC-DC converter.

In accomplishing the above objects, according to a first aspect of thepresent invention, there is provided a bidirectional DC-DC converterincluding: a first smoothing capacitor which is connected in parallelwith a first DC power supply and connected between DC terminals of afirst switching circuit; a second smoothing capacitor which is connectedin parallel with a second DC power supply and connected between DCterminals of a second switching circuit; a primary winding which isconnected between AC terminals of the first switching circuit; asecondary winding which is connected between AC terminals of the secondswitching circuit; a transformer which magnetically couples the primarywinding to the secondary winding; a control section which controls thefirst and the second switching circuits so as to transfer electricalpower between the first and the second DC power supplies; a first diodewhich is inserted in series between the first DC power supply, the firstsmoothing capacitor, and the DC terminals of the first switching circuitto ensure that a cathode faces a positive electrode of the first DCpower supply; and a first switch which is connected in parallel with thefirst diode; wherein the control section turns on the first switch whensupplying electrical power from the first DC power supply to the secondDC power supply and turns off the first switch when supplying electricalpower from the second DC power supply to the first DC power supply.

According to a second aspect of the present invention, there is providedthe bidirectional DC-DC converter further including a resonant reactorwhich is inserted in series with the primary winding and/or thesecondary winding.

According to a third aspect of the present invention, there is providedthe bidirectional DC-DC converter further including a resonant capacitorwhich is inserted in series with the primary winding and/or thesecondary winding.

According to a fourth aspect of the present invention, there is providedthe bidirectional DC-DC converter, wherein the first switching circuitincludes: a first switching leg which is connected in series with afirst and a second switching device; and a second switching leg which isconnected in series with a third and a fourth switching device andconnected in parallel with the first switching leg, wherein both ends ofthe first switching leg are a pair of DC terminals, and wherein a seriesconnection point between the first and the second switching devices anda series connection point between the third and the fourth switchingdevices are a pair of AC terminals.

According to a fifth aspect of the present invention, there is providedthe bidirectional DC-DC converter, wherein the third and the fourthswitching devices are replaced with a first capacitor and a secondcapacitor, respectively.

According to a sixth aspect of the present invention, there is providedthe bidirectional DC-DC converter, wherein the primary winding includesa connection between one end of a first primary winding and one end of asecond primary winding; wherein the first switching circuit includes afirst and a second switching device; wherein the other end of the firstprimary winding is connected to one end of the first switching device;wherein the other end of the second primary winding is connected to oneend of the second switching device; wherein the other end of the firstswitching device is connected to the other end of the second switchingdevice; and wherein a connection point between the first and the secondswitching devices and a connection point between the first and thesecond primary windings are a pair of DC terminals.

According to a seventh aspect of the present invention, there isprovided the bidirectional DC-DC converter, wherein the second switchingcircuit includes a smoothing reactor, a third switching leg which isconnected in series with a fifth and a sixth switching device, and afourth switching leg which is connected in series with a seventh and aneighth switching device and connected in parallel with the thirdswitching leg; wherein one end of the smoothing reactor is connected toone end of the third switching leg; wherein the other end of thesmoothing reactor and the other end of the third switching leg are apair of DC terminals; and wherein a series connection point between thefifth and the sixth switching devices and a series connection pointbetween the seventh and the eighth switching devices are a pair of ACterminals.

According to an eighth aspect of the present invention, there isprovided the bidirectional DC-DC converter, wherein the secondarywinding includes a connection between one end of a first secondarywinding and one end of a second secondary winding; wherein the secondswitching circuit includes a smoothing reactor, a fifth switchingdevice, and a sixth switching device; wherein the other end of the firstsecondary winding is connected to one end of the fifth switching device;wherein the other end of the second secondary winding is connected toone end of the sixth switching device; wherein the other end of thefifth switching device is connected to the other end of the sixthswitching device; wherein one end of the smoothing reactor is connectedto a connection point between the first and the second secondarywindings; and wherein the other end of the smoothing reactor and aconnection point between the fifth and the sixth switching devices are apair of DC terminals.

According to a ninth aspect of the present invention, there is providedthe bidirectional DC-DC converter, wherein the second switching circuitincludes a connection between one end of a first smoothing reactor andone end of a second smoothing reactor, and a connection between one endof a fifth switching device and one end of a sixth switching device;wherein the other end of the fifth switching device is connected to theother end of the first smoothing reactor; wherein the other end of thesixth switching device is connected to the other end of the secondsmoothing reactor; wherein the other end of the fifth switching deviceand the other end of the sixth switching device are a pair of ACterminals; and wherein a connection point between the first and thesecond smoothing reactors and a connection point between the fifth andthe sixth switching devices are a pair of DC terminals.

According to a tenth aspect of the present invention, there is providedthe bidirectional DC-DC converter further including: a second diodewhich is inserted in series between the second DC power supply, thesecond smoothing capacitor, and the DC terminals of the second switchingcircuit to ensure that a cathode faces a positive electrode of thesecond DC power supply; and a second switch which is connected inparallel with the second diode; wherein the control section turns on thesecond switch when supplying electrical power from the second DC powersupply to the first DC power supply and turns off the second switch whensupplying electrical power from the first DC power supply to the secondDC power supply.

According to an eleventh aspect of the present invention, there isprovided the bidirectional DC-DC converter, wherein the second switchingcircuit includes a third switching leg, which is connected in serieswith a fifth and a sixth switching device, and a fourth switching leg,which is connected in series with a seventh and an eighth switchingdevice and connected in parallel with the third switching leg; whereinboth ends of the third switching leg are a pair of DC terminals; andwherein a series connection point between the fifth and the sixthswitching devices and a series connection point between the seventh andthe eighth switching devices are a pair of AC terminals.

According to a twelfth aspect of the present invention, there isprovided the bidirectional DC-DC converter, wherein the seventh and theeighth switching devices are replaced with a third capacitor and afourth capacitor, respectively.

According to a thirteenth aspect of the present invention, there isprovided the bidirectional DC-DC converter, wherein the secondarywinding includes a connection between one end of a first secondarywinding and one end of a second secondary winding; wherein the secondswitching circuit includes a fifth and a sixth switching device; whereinthe other end of the first secondary winding is connected to one end ofthe fifth switching device; wherein the other end of the secondsecondary winding is connected to one end of the sixth switching device;wherein the other end of the fifth switching device is connected to theother end of the sixth switching device; and wherein a connection pointbetween the fifth and the sixth switching devices and a connection pointbetween the first and the second secondary windings are a pair of DCterminals.

According to a fourteenth aspect of the present invention, there isprovided the bidirectional DC-DC converter, wherein the first and thesecond switches are electromagnetic relays.

According to a fifteenth aspect of the present invention, there isprovided the bidirectional DC-DC converter, wherein the first to theeighth switching devices are MOSFETs.

According to a sixteenth aspect of the present invention, there isprovided the bidirectional DC-DC converter, wherein the first and thesecond diodes exhibit faster reverse recovery characteristics than bodydiodes and/or antiparallel diodes of the first to the eighth switchingdevices.

In accomplishing the above objects, according to a seventeenth aspect ofthe present invention, there is provided a method for controlling abidirectional DC-DC converter comprising: a first switching circuitconnected in parallel with a first DC power supply; a second switchingcircuit connected in parallel with a second DC power supply; a primarywinding connected between AC terminals of the first switching circuit; asecondary winding connected between AC terminals of the second switchingcircuit; a transformer for magnetically coupling the primary winding tothe secondary winding; and a control section for controlling the firstand the second switching circuits so as to transfer electrical powerbetween the first and the second DC power supplies, the method includingthe steps of: inserting a first rectifying device in series between thefirst DC power supply and DC terminals of the first switching circuit toensure that the direction of rectification is oriented toward a positiveelectrode of the first DC power supply; and connecting a first switch inparallel with the first rectifying device; wherein the control sectionturns on the first switch when supplying electrical power from the firstDC power supply to the second DC power supply and turns off the firstswitch when supplying electrical power from the second DC power supplyto the first DC power supply.

The present invention makes it possible to provide a small-size,high-efficiency, bidirectional DC-DC converter that permits the use of ahigh-voltage MOSFET or other switching device having fast switchingcharacteristics and relatively slow body diode reverse recoverycharacteristics, exhibits low switching loss, and reduces the influenceof relatively slow body diode reverse recovery characteristics.

BRIEF DESCRIPTION OF THE DRAWINGS

Embodiment of the present invention will be described in detail based onthe following figures, wherein:

FIG. 1 is a schematic circuit diagram of a bidirectional DC-DC converteraccording to a first embodiment of the present invention;

FIG. 2 is a schematic circuit diagram of a bidirectional DC-DC converteraccording to a second embodiment of the present invention;

FIG. 3 is circuit diagram illustrating how the bidirectional DC-DCconverter according to the second embodiment achieves forward powertransmission;

FIG. 4 is circuit diagram illustrating how the bidirectional DC-DCconverter according to the second embodiment achieves backward powertransmission; and

FIG. 5 is a schematic circuit diagram of a bidirectional DC-DC converteraccording to a third embodiment of the present invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

Embodiments of the present invention will now be described in detailwith reference to the accompanying drawings.

In this document, electrical power transmission from a DC power supplyV1 to a DC power supply V2 is referred to as forward power transmission,whereas electrical power transmission from the DC power supply V2 to theDC power supply V1 is referred to as backward power transmission.Further, the voltage of a switching device in the ON state or a voltageequivalent to or lower than a forward dropped voltage of a diode isreferred to as the zero voltage. Moreover, reducing switching loss bychanging the state of a switching device between ON and OFF while thezero voltage is applied to the switching device is referred to aszero-voltage switching.

First Embodiment

FIG. 1 is a schematic circuit diagram of a bidirectional DC-DC converteraccording to a first embodiment of the present invention. Thebidirectional DC-DC converter is connected between the DC power supplyV1 and the DC power supply V2 to transfer electrical power between theDC power supply V1 and the DC power supply V2. A load R1 is connected tothe DC power supply V1, whereas a load R2 is connected to the DC powersupply V2.

Referring to FIG. 1, a smoothing capacitor C1 is connected to the DCpower supply V1, whereas a smoothing capacitor C2 is connected to the DCpower supply V2. The DC terminals of a switching circuit 11 areconnected to the smoothing capacitor C1 through a diode D1. Theconnection of this diode D1 is oriented so that electrical power flowsfrom the switching circuit 11 to the DC power supply V1 and does notflow from the DC power supply V1 to the switching circuit 11. A switchSW1 is connected in parallel with the diode D1. Further, the DCterminals of a switching circuit 12 are connected to the smoothingcapacitor C2.

A winding N1 is connected to the AC terminals of the switching circuit11. A winding N2 is connected to the AC terminals of the switchingcircuit 12. A transformer 2 magnetically couples the winding N1 to thewinding N2.

The switching circuit 11, switching circuit 12, and switch SW1 arecontrolled by a control section 1. The control section 1 is connected tovoltage sensors 21, 22 and current sensors 31, 32.

An operation that the bidirectional DC-DC converter according to thefirst embodiment performs for forward power transmission will now bedescribed. The control section 1 maintains the switch SW1 in the ONstate and applies an AC voltage to the winding N1 by allowing theswitching circuit 11 to perform a switching operation. The switchingcircuit 12 rectifies a voltage induced across the winding N2 andsupplies electrical power to the DC power supply V2.

As described above, the switch SW1 is maintained in the ON state duringforward power transmission. As this forms a short circuit across thediode D1, the DC terminals of the switching circuit 11 are in the samestate as when they are directly connected to the smoothing capacitor C1,bypassing the diode D1. The resulting circuit configuration isequivalent to the circuit configuration described in JP-A No.2002-165448, JP-A No. 2006-187147, and JP-A No. 2004-282828. Therefore,the switching operation can be performed in the same manner as describedin JP-A No. 2002-165448, JP-A No. 2006-187147, and JP-A No. 2004-282828.

Next, an operation that the bidirectional DC-DC converter according tothe first embodiment performs for backward power transmission will nowbe described. The control section 1 maintains the switch SW1 in the OFFstate and applies an AC voltage to the winding N2 by allowing theswitching circuit 12 to perform a switching operation. The switchingcircuit 11 rectifies a voltage induced across the winding N1 andsupplies electrical power to the DC power supply V1.

As described above, when backward power transmission occurs, theswitching circuit 11 functions as a rectifier circuit with the switchSW1 maintained in the OFF state. In this instance, even if a body diodeof a high-voltage MOSFET or other device exhibiting relatively slowreverse recovery characteristics is used as a rectifying deviceconstituting the switching circuit 11, the diode D1, which exhibitsrelatively fast reverse recovery characteristics, prevents a reverseelectrical power flow from the DC power supply V1 and smoothingcapacitor C1 to the switching circuit 11. This enables the bidirectionalDC-DC converter according to the present invention to achieve backwardpower transmission with high efficiency. When a conventional circuitconfiguration, which does not include the diode D1, is employed, it isreadily understood that effective backward power transmission isobstructed because electrical power flows in the reverse direction fromthe DC power supply V1 and smoothing capacitor C1 to the switchingcircuit 11 during a reverse conduction period of the rectifying device.

The above-mentioned problem can also be solved by using an IGBT with anantiparallel diode as a switching/rectifying device for the switchingcircuit 11 instead of using the above-described embodiment. However, theIGBT suffers an increase in the switching loss and a decrease in theefficiency of forward power transmission because it exhibits slowerswitching characteristics than a high-voltage MOSFET. Further, if aswitching frequency is decreased to reduce the switching loss, it isnecessary to increase the sizes of the transformer 2 and smoothingcapacitors C1, C2. This will result in an increase of the cubic volumeof the bidirectional DC-DC converter.

Another method of solving the above-mentioned problem without using thepresent invention is to use a reverse-blocking MOSFET with anantiparallel diode as a switching/rectifying device for the switchingcircuit 11. However, the use of this method will increase the cost andthe cubic volume due to an increase in the number of parts.

Meanwhile, the switch SW1 in the bidirectional DC-DC converter accordingto the present invention changes its state between ON and OFF only whena switch is made to initiate forward power transmission or backwardpower transmission. Therefore, the bidirectional DC-DC converteraccording to the present invention can use an IGBT, which operates at arelatively low speed, or a mechanical switch such as an electromagneticrelay. If an IGBT package with a built-in antiparallel diode is usedwhen the use of an IGBT is demanded, it is not necessary to use thediode D1 as an external device, thereby making it easy to reduce thesize of the bidirectional DC-DC converter. Further, if the mechanicalswitch is used, it makes it possible to achieve forward powertransmission with increased efficiency because it exhibits lowconduction loss.

Second Embodiment

FIG. 2 is a schematic circuit diagram of a bidirectional DC-DC converteraccording to a second embodiment of the present invention. Thebidirectional DC-DC converter transfers electrical power between a DCpower supply V1 and a DC power supply V2, which are connected toopposite ends of the bidirectional DC-DC converter. A load R1 isconnected to the DC power supply V1, whereas a load R2 is connected tothe DC power supply V2.

Referring to FIG. 2, a smoothing capacitor C1 is connected to the DCpower supply V1, whereas a smoothing capacitor C2 is connected to the DCpower supply V2. Switching devices H1, H2 are connected in series with afirst switching leg. The first switching leg is connected to thesmoothing capacitor C1 through a diode D1. The connection of this diodeD1 is oriented so that electrical power flows from the first switchingleg to the DC power supply V1 and does not flow from the DC power supplyV1 to the first switching leg. A switch SW1 is connected in parallelwith the diode D1. Switching devices H3, H4 are connected in series witha second switching leg. The second switching leg is connected inparallel with the first switching leg. A winding N1, a resonant reactorLr, and a resonant capacitor Cr are connected in series between a seriesconnection point of the switching devices H1 and H2 and a seriesconnection point of the switching devices H3 and H4.

A transformer 3 magnetically couples windings N1, N21, and N22. One endof the winding N21 is connected to one end of the winding N22. The otherend of the winding N21 is connected to one end of a switching device 51.The other end of the winding N22 is connected to one end of a switchingdevice S2. The other end of the switching device S1 and the other end ofthe switching device S2 are connected to one end of the smoothingcapacitor C2. A connection point between the winding N21 and the windingN22 is connected to the other end of the smoothing capacitor C2 througha smoothing reactor L.

A voltage clamp circuit, which is formed by connecting one end each ofthe switching device S3, switching device S4, and clamp capacitor Cc, isconfigured by connecting the other end of the switching device S3 to oneend of the switching device S1, connecting the other end of theswitching device S4 to one end of the switching device S2, andconnecting the other end of the clamp capacitor Cc to the other ends ofthe switching device S1 and switching device S2.

Antiparallel diodes DH1-DH4, DS1-DS4 are connected to the switchingdevices H1-H4, S1-S4, respectively. If MOSFETs are used as theseswitching devices, MOSFET body diodes can be used as the antiparalleldiodes.

The switching devices H1-H4, S1-S4 and switch SW1 are controlled by acontrol section 1. The control section 1 is connected to voltage sensors21, 22 and current sensors 31, 32.

[Forward Power Transmission from V1 to V2]

FIG. 3 shows circuit diagrams (a) to (f) illustrating how thebidirectional DC-DC converter according to the second embodimentachieves forward power transmission. Forward power transmissionoperations will now be described in detail with reference to FIG. 3. InFIG. 3, (a) to (f) depict modes a to f, respectively.

(Mode a)

In mode a, the switch SW1 and switching devices H1 and H4 are ON,whereas the switching devices H2 and H3 are OFF. The voltage of the DCpower supply V1 is applied to the winding N1 through the switch SW1,switching devices H1 and H4, resonant capacitor Cr, and resonant reactorLr.

The switching devices S2 and S3 are OFF so that a voltage developedacross the winding N21 is applied to the DC power supply V2 through thediode DS1 and smoothing reactor L. Consequently, energy is supplied tothe DC power supply V2. Further, a voltage developed across the windingsN21 and N22 is applied to the clamp capacitor Cc through the diodes DS1and DS4. Consequently, the clamp capacitor Cc is charged.

If MOSFETs are used as the switching devices S1-S4, the loss may bereduced by shunting the current in the diodes DS1 and DS4 to theswitching devices S1, S4 while the switching devices S1 and S4 are ON.Reducing the loss by turning ON a MOSFET in a situation where a diode'sforward current flows to a diode antiparallelly connected to the MOSFETor a body diode of the MOSFET is hereinafter referred to as synchronousrectification. In this instance, the switching device S4 is turned ON(zero-voltage switching).

(Mode b)

The charging current for the clamp capacitor Cc decreases, and beforelong, the clamp capacitor Cc changes into a discharge state. The currentdischarged from the clamp capacitor Cc is supplied to the DC powersupply V2 through the switching device S4, winding N22, and smoothingreactor L.

(Mode c)

When the switching device H4 is turned OFF, the current in the switchingdevice H4 flows to a diode DH3, switching device H1, resonant capacitorCr, resonant reactor Lr, and winding N1. In this instance, the switchingdevice H3 is turned ON (zero-voltage switching).

When the switching device S4 is turned OFF, the discharge of the clampcapacitor Cc terminates so that the current in the switching device S4is diverted to the diode DS2. If the switching device S2 turns ON inthis instance, synchronous rectification occurs. The energy stored inthe smoothing reactor L is supplied to the DC power supply V2.

(Mode d)

When the switching device H1 is turned OFF, the current in the switchingdevice H1 flows in the switch SW1 and/or diode D1, DC power supply V1,diode DH2, resonant capacitor Cr, resonant reactor Lr, winding N1, anddiode DH3. In this instance, the switching device H2 is turned ON(zero-voltage switching). The voltage of the DC power supply V1 isapplied to the resonant reactor Lr so that the current decreases.

(Mode e)

The switching devices H2 and H3 are ON. Therefore, after the current inthe resonant reactor Lr is reduced to zero, the current increasesinversely. This decreases the current in the diode DS1 and winding N21and increases the current in the diode DS2 and winding N22. Theswitching device S1 is turned OFF before the current in the winding N21is reduced to zero.

(Mode f)

When the current in the winding N21 is reduced to zero, the diode DS1goes into reverse conduction, and then achieves reverse recovery. Uponreverse recovery, the current flowing during such reverse conduction isdiverted to the diode DS3. In this instance, the switching device S3 isturned ON (zero-voltage switching). Further, the voltage of the DC powersupply V1 is applied to the winding N1.

The switching devices S1 and S4 are OFF so that a voltage developedacross the winding N22 is applied to the DC power supply V2 through thediode DS2 and smoothing reactor L. Consequently, energy is supplied tothe DC power supply V2. Further, a voltage developed across the windingsN21 and N22 is applied to the clamp capacitor Cc through the diodes DS2and DS3. Consequently, the clamp capacitor Cc is charged.

The operation performed in mode f is symmetrical to the operationperformed in mode a. Subsequently, the bidirectional DC-DC converterperforms symmetrical operations in modes b to e, and then reverts tomode a. As such operations can be readily understood, no furtherdetailed description will be given here.

[Backward Power Transmission from V2 to V1]

FIG. 4 shows circuit diagrams (A) to (H) illustrating how thebidirectional DC-DC converter according to the second embodimentachieves backward power transmission. Backward power transmissionoperations will now be described in detail with reference to FIG. 4. InFIG. 4, (A) to (H) depict modes A to H, respectively.

(Mode A)

In mode A, the switching devices S1 and S2 are ON, whereas the switchingdevices S3 and S4 are OFF. The voltage of the DC power supply V2 isapplied to the smoothing reactor L through the windings N21 and N22, andswitching devices S1 and S2, so that the smoothing reactor L stores theenergy of the DC power supply V2.

Further, the switch SW1 and switching devices H1 and H4 are OFF, whereasthe switching devices H2 and H3 are ON. The current in the resonantcapacitor Cr, diodes DH1 and DH4, switching devices H2 and H3, andwinding N1 flows to the resonant reactor Lr. If, in this instance,MOSFETs are used as the switching devices H1-H4, synchronousrectification occurs when the switching devices H1 and H4 are turned ON.

(Mode B)

When the switching device S2 is turned OFF, the current in the switchingdevice S2 flows in the diode DS4 to charge the clamp capacitor Cc. Inthis instance, the switching device S4 is turned ON (zero-voltageswitching).

The voltage of the clamp capacitor Cc is applied to the windings N21 andN22 to develop a voltage across the winding N1. The voltage developedacross the winding N1 is applied to the resonant reactor Lr to increasethe current in the resonant reactor Lr.

Further, the energy stored in the smoothing reactor L is released.

(Mode C)

When the switching devices H2 and H3 are turned OFF, the current in theswitching devices H2 and H3 flows to the DC power supply V1 through thediode DH4, winding N1, resonant reactor Lr, resonant capacitor Cr, diodeDH1, and diode D1, thereby supply energy to the DC power supply V1. Inthis instance, the switching devices H1 and H4 are turned ON(zero-voltage switching).

(Mode D)

The charging current for the clamp capacitor Cc decreases in accordancewith an increase in the current in the resonant reactor Lr. Before long,the clamp capacitor Cc changes into a discharge state.

(Mode E)

When the switching device S4 is turned OFF, the current discharged fromthe clamp capacitor Cc, which was flowing to the switching device S4,flows in the diode DS2. In this instance, the switching device S2 isturned ON (zero-voltage switching).

As the voltage VCc of the clamp capacitor Cc is no longer applied to thewindings N21 and N22, no voltage is developed across the winding N1.Therefore, the voltage of the DC power supply V1 is applied to theresonant reactor Lr. This decreases the current in the resonant reactorLr.

Further, the smoothing reactor L stores the energy of the DC powersupply V2 in the same manner as in mode A.

(Mode F)

The direction of the current in the switching device S2 reverses inaccordance with a decrease in the current in the resonant reactor Lr.

(Mode G)

The switching devices H1 and H4 are ON, whereas the switch SW1 is OFF.Therefore, when the current in the resonant reactor Lr further decreasesand reaches zero, the diode D1 goes into reverse conduction, and acurrent flows in the resonant reactor Lr in a direction opposite to thedirection of the current in mode F.

(Mode H)

When the diode D1 achieves reverse recovery, the current in the resonantreactor Lr, which is stored during a reverse conduction of the diode D1,causes the diodes DH2 and DH3 to conduct and flows in the diodes DH2 andDH3, resonant capacitor Cr, winding N1, and switching devices H1 and H4.In this instance, an electrical charge is stored in the resonantcapacitor Cr to generate a voltage in the direction of increasing thecurrent in the resonant reactor Lr. Therefore, the current in theresonant reactor Lr gradually increases.

The operation performed in mode H is symmetrical to the operationperformed in mode A. Subsequently, the bidirectional DC-DC converterperforms symmetrical operations in modes B to G, and then reverts tomode A. As such operations can be readily understood, no furtherdetailed description will be given here.

During mode A (H), the diodes DH2 (DH1) and DH3 (DH4) achieve reverserecovery. However, when MOSFET body diodes or other diodes havingrelatively slow reverse recovery characteristics are used as the diodesDH1-DH4, they may fail to achieve reverse recovery during mode A (H).Even if the diodes DH2 and DH3 do not achieve reverse recovery duringmode A, the subsequent operation is the same as described above as faras reverse recovery is achieved during mode B. If reverse recovery isstill not achieved during mode B, the bidirectional DC-DC converterproceeds to operate in mode C as soon as reverse recovery is achieved.However, if the bidirectional DC-DC converter switches from a mode Boperation to a mode C operation with a delay, the output power mayincrease. In such an instance, the diodes DH2 and DH3 should be allowedto achieve reverse recovery before the end of a mode B period for thepurpose of adjusting the output power to a desired value with ease. Assuch being the case, a later-described method of connecting anadditional capacitance component in parallel with the diode D1 can beused.

If, in mode A (H), a capacitance component is connected in parallel withthe diode D1, a current flows to charge the capacitance component afterreverse recovery is achieved by the diode D1. Also during a period inwhich such a charging current flows, the resonant reactor Lr stores thecurrent. If, for instance, a capacitor is connected in parallel with thediode D1, it is possible to increase the current in the resonant reactorLr in mode A (H). An increase in the current in the resonant reactor Lrwill facilitate the reverse recovery of the diodes DH2 (DH1) and DH3(DH4).

However, if a large current flows in the resonant reactor Lr in mode A(H), it is likely that the switching devices S1 and S2 may fail toachieve zero-voltage switching when they turn ON. If, in mode A, thecurrent in the resonant reactor Lr, that is, the current in the windingN1, is large, the current in the winding N21 and switching device S1 islarger than the current in the winding N22 and switching device S2because the windings N1, N21 and N22 are magnetically coupled. In modeB, the current interrupted by the switching device S2 is the chargingcurrent for the clamp capacitor Cc. Therefore, if the interruptedcurrent is decreased, the charging current for the clamp capacitor Cc isdecreased in modes B and C. Consequently, the current discharged fromthe clamp capacitor Cc in mode D is also decreased. The reason is that,in mode E, the switching device S4 interrupts the current dischargedfrom the clamp capacitor Cc to divert the interrupted current to thediode DS2, thereby achieving zero-voltage switching when the switchingdevice S2 turns ON.

In view of the above circumstances, the upper limit for the ON timeratio of the switching devices S1 and S2 can be varied in accordancewith an input voltage, that is, the voltage of the DC power supply V2,to make it easy for the switching devices S1 and S2 to achievezero-voltage switching when they turn ON even if the current in theresonant reactor Lr is relatively large in mode A (H). Increasing the ONtime ratio of the switching devices S1 and S2 not only increases theoutput power but also increases the voltage of the clamp capacitor Cc.An increase in the voltage of the clamp capacitor Cc may break down theswitching devices S1-S4 because the voltage of the clamp capacitor Cc isapplied to the switching devices S1-S4. Therefore, an upper limit isimposed on the ON time ratio of the switching devices S1 and S2. If theoutput power is insufficient even when the ON time ratio is at the upperlimit, desired output power is obtained by lengthening the mode B periodwhile the ON time ratio is at the upper limit. In this instance, theoutput power is adjusted by varying the length of the mode B period. Ifsufficient output power is obtained even when the mode B period isreduced to zero, that is, the switching devices H2 and H3 are turned OFFin mode C at substantially the same time as the switching device S2 isturned OFF in mode B, the output power may be adjusted by varying the ONtime ratio of the switching devices S1 and S2 while the length of themode B period is fixed, for instance, at zero.

However, if the mode B period is lengthened in order to obtainsufficient output power, it is likely that the switching devices S1 andS2 may fail to achieve zero-voltage switching when they turn ON. In modeB, the voltage developed across the winding N1 is substantially entirelyapplied to the resonant reactor Lr. Therefore, the current in theresonant reactor Lr rapidly increases. Consequently, the chargingcurrent for the clamp capacitor Cc rapidly decreases to reduce thequantity of electrical charge in modes B and C. Thus, the currentdischarged from the clamp capacitor Cc in mode D also decreases. Thereason is that, in mode E, the switching device S4 interrupts thecurrent discharged from the clamp capacitor Cc to divert the interruptedcurrent to the diode DS2, thereby achieving zero-voltage switching whenthe switching device S2 turns ON.

In a situation where desired output power is obtained by keeping the ONtime ratio of the switching devices S1 and S2 at an upper limit andchanging the length of the mode B period for output power adjustmentpurposes as described earlier, desired output power can also be obtainedby raising the upper limit for the ON time ratio to shorten the mode Bperiod. In this situation, therefore, it is likely that the switchingdevices S1 and S2 may achieve zero-voltage switching when they turn ON.In such an instance, the breakdown of the switching devices S1-S4, whichmay result from an increase in the voltage of the clamp capacitor Cc,can be avoided by raising the upper limit for the ON time ratio inaccordance with a decrease in the input voltage, that is, the voltage ofthe DC power supply V2. The reason is that when the ON time ratio isfixed, the voltage of the clamp capacitor Cc is substantiallyproportional to the input voltage, that is, the voltage of the DC powersupply V2.

As described above, even if the current in the resonant reactor Lr isrelatively increased in mode A (H) for the purpose of facilitating thereverse recovery of the diodes DH1-DH4, turning ON the switching devicesS1 and S2 is likely to achieve zero-voltage switching when the upperlimit for the ON time ratio of the switching devices S1 and S2 is variedin accordance with the input voltage, that is, the voltage of the DCpower supply V2.

The greatest feature of the bidirectional DC-DC converter according tothe second embodiment is that it maintains the switch SW1 in the ONstate during forward power transmission and in the OFF state duringbackward power transmission as described earlier. This ensures that evenif a high-voltage MOSFET body diode or other device exhibitingrelatively slow reverse recovery characteristics is used as the diodesDH1-DH4 during backward power transmission, the diode D1, which exhibitsrelatively fast reverse recovery characteristics, prevents a reverseelectrical power flow from the DC power supply V1 and smoothingcapacitor C1 to the diodes DH1-DH4, thereby providing efficient backwardpower transmission. This makes it possible to achieve backward powertransmission with high efficiency even when a high-voltage MOSFET andits body diode are used as the switching devices H1-H4 and diodesDH1-DH4.

The other features of the bidirectional DC-DC converter according to thesecond embodiment are the same as those of the first embodiment and willnot redundantly be described in detail except that it should be notedthat the switching devices H1-H4 and diodes DH1-DH4 of the bidirectionalDC-DC converter according to the second embodiment correspond to theswitching/rectifying device for the switching circuit 11 of thebidirectional DC-DC converter according to the first embodiment.

Further, it is assumed that the second embodiment uses the combinationof a voltage-type full-bridge circuit and a current-type center tapcircuit. However, the use of the combination of a voltage-type centertap circuit, a half-bridge circuit, a current-type full-bridge circuit,and a current doubler circuit will also provide the same configurationand effect as the second embodiment.

Third Embodiment

FIG. 5 is a schematic circuit diagram of a bidirectional DC-DC converteraccording to a third embodiment of the present invention. Thebidirectional DC-DC converter transfers electrical power between a DCpower supply V1 and a DC power supply V2, which are connected toopposite ends of the bidirectional DC-DC converter.

Referring to FIG. 5, a smoothing capacitor C1 is connected to the DCpower supply V1, whereas a smoothing capacitor C2 is connected to the DCpower supply V2. Switching devices H1 and H2 are connected in serieswith a first switching leg. The first switching leg is connected to thesmoothing capacitor C1 through a diode D1. The connection of this diodeD1 is oriented so that electrical power flows from the first switchingleg to the DC power supply V1 and does not flow from the DC power supplyV1 to the first switching leg. A switch SW1 is connected in parallelwith the diode D1. A winding N1, a resonant reactor Lr, and a resonantcapacitor Cr are connected in series across the switching device H2.

Switching devices S1 and S2 are connected in series with a twenty-firstswitching leg. The twenty-first switching leg is connected to thesmoothing capacitor C2 through a diode D2. The connection of this diodeD2 is oriented so that electrical power flows from the twenty-firstswitching leg to the DC power supply V2 and does not flow from the DCpower supply V2 to the twenty-first switching leg. A switch SW2 isconnected in parallel with the diode D2. Switching devices S3, S4 areconnected in series with a twenty-second switching leg. Thetwenty-second switching leg is connected in parallel with thetwenty-first switching leg. A winding N2 is connected between a seriesconnection point of the switching devices S1 and S2 and a seriesconnection point of the switching devices S3 and S4. A transformer 2magnetically couples the winding N1 to the winding N2.

Antiparallel diodes DH1, DH2, and DS1-DS4 are connected to the switchingdevices H1, H2, and S1-S4, respectively. When MOSFETs are used as theseswitching devices, MOSFET body diodes can be used as the antiparalleldiodes.

An operation performed by the bidirectional DC-DC converter according tothe third embodiment will now be described. During forward powertransmission, the switch SW1 is maintained in the ON state with theswitch SW2 maintained in the OFF state. The switching devices H1 and H2are turned ON/OFF complementarily so that an alternating resonantcurrent flows to the winding N1 through the resonant capacitor Cr andresonant reactor Lr. The diodes DS1-DS4 rectify a current induced in thewinding N2 so that electrical power is supplied to the DC power supplyV2 through the diode D2.

In this instance, even if devices exhibiting relatively slow reverserecovery characteristics are used as the diodes DS1-DS4, the diode D2,which exhibits relatively fast reverse recovery characteristics,prevents a reverse electrical power flow from the DC power supply V2 andsmoothing capacitor C2 to the diodes DS1-DS4, thereby achieving forwardpower transmission with high efficiency. It means that efficient forwardpower transmission can be achieved even when, for instance, ahigh-voltage MOSFET and its body diode are used as the switching devicesS1-S4 and diodes DS1-DS4.

During backward power transmission, on the other hand, the switch SW2 ismaintained in the ON state with the switch SW1 maintained in the OFFstate. The switching devices S1 and S2 are turned ON/OFFcomplementarily. In addition, the switching devices S4 and S3 are turnedON/OFF in synchronism with the switching devices S1 and S2 so that analternating resonant current flows to the winding N2. A current inducedin the winding N1 passes through the resonant capacitor Cr and resonantreactor Lr and is rectified by the diodes DH1 and DH2 so that electricalpower is supplied to the DC power supply V1 through the diode D1.

In this instance, even if devices exhibiting relatively slow reverserecovery characteristics are used as the diodes DH1 and DH2, the diodeD1, which exhibits relatively fast reverse recovery characteristics,prevents a reverse electrical power flow from the DC power supply V1 andsmoothing capacitor C1 to the diodes DH1 and DH2, thereby achievingbackward power transmission with high efficiency. It means thatefficient backward power transmission can be achieved even when, forinstance, a high-voltage MOSFET and its body diode are used as theswitching devices H1 and H2 and diodes DH1 and DH2.

In general, diodes tend to exhibit poor reverse recovery characteristicswhen their dielectric strength is high. However, the third embodimentmakes it possible to achieve bidirectional power conversion with highefficiency because it prevents a reverse electrical power flow from theDC power supplies V1 and V2 even when the voltages of both the DC powersupply V1 and DC power supply V2 are relatively high and all thedielectric strengths of the diodes DH1, DH2, and DS1-DS4 are relativelyhigh.

Effects produced by the diodes D1 and D2, and switches SW1 and SW2 willnot be described in detail because they are the same as described inconnection with the first and second embodiments.

It is assumed that the third embodiment uses the combination of asingle-ended push-pull circuit and a full-bridge circuit. However, thecombination of a half-bridge circuit and a center tap circuit may alsobe used.

As described above, the present invention produces the effects describedin this document when a switch equipped with an antiparallel diode isinserted between a smoothing capacitor and a switching circuit, whichare included in a voltage-type circuit of an isolated bidirectionalDC-DC converter. It is therefore obvious that the present invention canbe applied to a variety of isolated bidirectional DC-DC convertershaving a voltage-type circuit.

As described above, the present invention is applicable to allbidirectional DC-DC converters having an isolation function.

What is claimed is:
 1. A bidirectional DC-DC converter comprising: a first switching circuit to input electrical power from a first DC power supply, with which a first smoothing capacitor is connected in parallel, to an in-between terminal of DC terminals of the first switching circuit and to convert the electrical power to AC so as to supply the AC from an in-between terminal of AC terminals to a primary winding; a second switching circuit to input electrical power from a second DC power supply, with which a second smoothing capacitor is connected in parallel, to an in-between terminal of DC terminals of the second switching circuit and to convert the electrical power to AC so as to supply the AC from an in-between terminal of AC terminals to a secondary winding; a transformer which magnetically couples the primary winding to the secondary winding; and control means for controlling the first and second switching circuits so as to transfer electrical power between the first and second DC power supplies, wherein the first switching circuit includes: a first switching leg in which switching devices H1 and H2 are connected in series; and a second switching leg in which switching devices H3 and H4 are connected in series and which is connected in parallel with the first switching leg, wherein an in-between point of both ends of the first switching leg is the in-between terminal of the DC terminals while an interval between a point at which the switching devices H1 and H2 are connected in series and a point at which the switching devices H3 and H4 are connected in series is the in-between terminal of the AC terminals, and wherein the control means is provided with a mode which keeps all the switching devices H1 to H4 in an ON state upon supplying electrical power from the second DC power supply to the first DC power supply.
 2. The bidirectional DC-DC converter according to claim 1, wherein the second switching circuit is provided with a smoothing reactor to smooth electric current flowed into the second DC power supply, and wherein energy of the second DC power supply accumulated in the smoothing reactor is discharged when the state of the switching devices provided with the second switching circuit is switched over to supply the electrical power of the second DC power supply to the secondary winding. 